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UC3638 датащи(PDF) 7 Page - Texas Instruments |
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UC3638 датащи(HTML) 7 Page - Texas Instruments |
7 / 9 page 7 UC1638 UC2638 UC3638 APPLICATION INFORMATION (cont.) will be half way between ground and VCC, and will auto- matically track changes in VCC. For cases where a dif- ferent null point is desired, AREF can be tied to any voltage between VEE + 2V and VCC − 2V. Of course the user must also allow sufficient headroom for the triangle waveform. Once the system null point has been chosen, the trian- gle wave amplitude and PWM deadband must be pro- grammed. The amplitude of the triangle wave is determined by trading off noise immunity and gain re- quirements. In general, the larger the triangle wave am- plitude, the greater the immunity to premature termination of PWM pulses due to switching noise. How- ever, high amplitude triangle waves require a greater voltage swing at the output of the voltage amplifier which ultimately reduces forward loop gain. Programming the PWM deadband allows the user to trade off gain linearity requirements with power amplifier efficiency. If the modulator is configured as in Figure 1, motor current is alternately pulsed by diagonally oppo- site drive FETs when the servo loop is at null. By adjust- ing the deadband, the user can program the offset voltage at the input of the PWM comparators. This offset results in deadtime, or time when neither PWM signal is active. A minimum amount of deadtime is always recom- mended to provide cross conduction protection at the power amplifier. Setting the deadtime to this minimum level will provide the maximum motor stiffness or holding torque, at the expense of power losses in the output stage. These losses result from the fact that the power amplifier is always sourcing motor current, even at null. As deadtime is increased, amplifier losses at null be- come less, at the expense of nonlinearity in the gain function. Eventually, if the deadband voltage is in- creased to equal the amplitude of the triangle wave, er- ror voltages at the null point will result in no PWM pulsing, or a dead zone. After the triangle waveform am- plitude and deadband are selected, the operating fre- quency is easily set by proper selection of CT and RT. Referring to Figure 1, if the voltage supply rails are ±15V, and the desired triangle wave oscillator amplitude is 6V p-p, PVSET is set by: VPK − VVLY =5•VPVSET VPVSET = 6 5 = 1.2V If 1V of deadband is chosen: 5 − VDB =1V VDB =4V In order to select the programming resistors, a source current for the reference is first selected. For a 1mA source current: R3+R4+R5= 5 ISOURCE = 5 1mA =5k R3 = 5- VDB ISOURCE = 1V 1mA =1k R4 = VDB - VPVSET ISOURCE = 4V - 1.2V 1mA = 2.8k R5=5k − 1k − 2.8k = 1.2k All of the voltages described by these equations are ref- erenced to the negative supply rail. In other words, for a split supply system, VREF is actually a negative voltage referenced to ground. The oscillator frequency is programmed by proper se- lection of RT and CT. If 220pF is chosen for CT, and an operating frequency of 30kHz is desired, RT is chosen by: F= 1 5RTCT •• 30kHz = 1 5 220pF RT •• RT = 30k With RT = 30k, the charge current out of the RT pin is limited to 1.2V 30k =40 µA, which is well within the specified maximum of 1mA. To calculate the actual deadtime or minimum time be- tween PWM pulses (TDB), the ratio of the deadband voltage to the triangle wave amplitude is multiplied by half the oscillator period: TDB = DB VPK - VVLY 1 f • = 5- VDB 5 VPVSET (5 RT CT) • •• • = (5 - VDB) RT CT VPVSET •• For this example the deadtime is: TDB = 1 30k 220pF 1.2 •• = 5.5 µsec If voltage feedforward is desired, PVSET should be de- rived off of the supply rails instead of VREF. This way changes in the supply voltage will linearly regulate the modulator gain, which decreases control loop suscepti- bility to line voltage variations. Since the voltage on the RT pin is a buffered version of PVSET, charge current tracks oscillator amplitude, and therefore the frequency |
Аналогичный номер детали - UC3638 |
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Аналогичное описание - UC3638 |
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